Minimum Return Power Control for Three-Level Dual Active Hybrid Full-Bridge DC-DC Converters

doi:10.16183/j.cnki.jsjtu.2021.493

Abstract

Abstract:

Hybrid three-level full bridge (H-TLFB) DC-DC converters increase the input voltage range by introducing a three-level bridge arm. Aimed at the problems of large power return and high current stress in the traditional dual phase shift control, a minimum return power control strategy is proposed. First, the power transmission characteristics of H-TLFB DC-DC converter are analyzed, the size of the return power value of the converter in two different operating modes is compared, and the optimal shift of the return power is calculated according to the mathematical relationship between the return power and the voltage ratio, the shift and the transmission power. The corresponding optimal shift of the return power is calculated, and the corresponding optimization control strategy is designed. Compared with the traditional dual phase shift control strategy, the return power in the minimum return power control strategy can reach the minimum value in the full power transmission range, and within a certain voltage ratio range, the return power and current stress can be optimized at the same time. Finally, the correctness and feasibility of the design control strategy are verified by experiments.

Key words: hybrid three-level full bridge (H-TLFB) DC-DC converter, phase shift control, backflow power, transmission efficiency, current stress

CLC Number:

TM564

TAO Haijun, ZHANG Jinsheng, XIAO Qunxing, ZHENG Zheng. Minimum Return Power Control for Three-Level Dual Active Hybrid Full-Bridge DC-DC Converters[J]. Journal of Shanghai Jiao Tong University, 2023, 57(5): 521-532.

Figures/Tables 25

Fig.1

Fig.2

Fig.3

Tab.1

Equivalent inductance current in Mode A

$i L r$ (t)	0≤D₁≤D₂≤1
$i L r$ (t₀)	[V₁(D₁-1)-nV₂(D₁+2D₂-1)]/(4L_rf_s)
$i L r$ (t₁)	[V₁(D₁-1)-nV₂(-D₁+2D₂-1)]/(4L_rf_s)
$i L r$ (t₂)	[V₁(-D₁+2D₂-1)-nV₂(D₁-1)]/(4L_rf_s)
$i L r$ (t₃)	[V₁(D₁+2D₂-1)-nV₂(D₁-1)]/(4L_rf_s)

Tab.1

Tab.2

Equivalent inductance current in Mode B

$i L r$ (t)	0≤D₂≤D₁≤1
$i L r$ (t₀)	[V₁(D₁-1)-nV₂(D₁+2D₂-1)]/(4L_rf_s)
$i L r$ (t₁)	[V₁(D₁-1)+nV₂(1-D₁)]/(4L_rf_s)
$i L r$ (t₂)	[V₁(D₁-1)+nV₂(1-D₁)]/(4L_rf_s)
$i L r$ (t₃)	[V₁(D₁+2D₂-1)+nV₂(1-D₁)]/(4L_rf_s)

Tab.2

Tab.3

Transmission power and reflux power values of converter in Mode A

模式A	功率表达式
$P t *$	4D₂-4 $D 22$ -2 $D 12$
$P c *$	[k(1-D₁)+2D₂-D₁-1]²/[2(k+1)]

Tab.3

Tab.4

Transmission power and reflux power values of converter in Mode B

模式B	功率表达式
$P t *$	4D₂-4D₁D₂-2 $D 22$
$P c *$	[(k-1)(1-D₁)]²/(2k)

Tab.4

Fig.4

Fig.5

Fig.6

Tab.5

Optimal shift comparison combinations in Mode B

P₀	D_1,Bmin	D_2,Bmin
0<P₀≤1/2	1- $P 0 / 2$	$P 2 / 2$
1/2<P₀≤2/3	$2 + 4 - 6 P 0 6$	$2 + 4 - 6 P 0 6$

Tab.5

Tab.6

Optimal shift comparison of different transmission power ranges

P₀	k	D_1,min
0<P₀≤1/2	k≥1	1- $P 0 / 2$
1/2<P₀<2/3	1≤k<k₂	$2 + 4 - 6 P 0 6$
	k≥k₂	(1+k) $1 - P 0 2 (k + 1) 2 + 4$
2/3≤P₀≤1	k≥1	(1+k) $1 - P 0 2 (k + 1) 2 + 4$

Tab.6

Tab.7

Optimal shift corresponding to minimum return power value

D_1,min	D_2,min	$P c, m i n *$
1- $P 0 / 2$	$P 0 / 2$	$P 0 (k - 1) 2 4 k$
$2 + 4 - 6 P 0 6$	$2 + 4 - 6 P 0 6$	$[(k - 1) (4 - 4 - 6 P 0)] 2 72 (k + 1)$
(1+k) $1 - P 0 2 (k + 1) 2 + 4$	$12 - 1 - P 0 2 (k + 1) 2 + 4$	$k - (1 - P 0) (k 2 + 2 k + 3) 2 2 2 (k + 1)$

Tab.7

Fig.7

Fig.8

Fig.9

Fig.10

Fig.11

Fig.12

Tab.8

Fig.13

Fig.14

Fig.15

Fig.16

Fig.17

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主电路参数	取值
f_s/kHz	10
n	1
L_r/μH	60
C₁, C₂/mF	0.25
C₃/mF	1